Multiport amplifier input network with compensation for output network gain and phase frequency response imbalance

ABSTRACT

Beamforming channels of a satellite are calibrated using a low power, spread spectrum calibration signal. The power of the calibration signal is below the noise level of a user signal in an active channel, allowing channels to be calibrated while active. When calibrating the transmit side circuitry, a two-stage calibration can be used, first calibrating the output hybrid matrix, then calibrating the whole of the transmit side. To improve performance, the dwell time spend calibrating a channel can be based on the power of the user signal in the channel. A transmit probe can be used to inject a calibration signal into the receive antennae and a receive probe can be used to extract the calibration signal from the transmit antennae. To reduce frequency of calibrations, the calibrations can be based on path-to-path differences. These techniques are also applied to multiport amplifiers (MPAs).

PRIORITY CLAIM

This application is a continuation-in-part (CIP) of and claims priorityto commonly invented and commonly assigned U.S. patent application Ser.No. 15/833,351, filed Dec. 6, 2017, and titled CALIBRATION OF SATELLITEBEAMFORMING CHANNELS, both of which are incorporated herein by reference

BACKGROUND

In order to properly transmit signals to subscribers, a communicationsatellite needs to be accurately calibrated. Although a satellite may beinitially well-calibrated, over time, and particularly in the harshconditions of space, the calibration can drift, requiring recalibration.Beamforming satellites transmit a signal from several antennae that forma beam at chosen locations though constructive and destructiveinterference between the different signals. Beamforming satellites mustbe calibrated to a set of requirements that are tighter than those for anon-beamforming satellite as the gain, phase and delay must beaccurately calibrated so that the different transmitted signalsconstructively interfere properly at the desired location.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram describing a satellite communication system.

FIG. 2A is a block diagram of a satellite or other beamforming apparatusfor an example of two input ports and two output ports.

FIGS. 2B and 2C provide more detail on the receive paths and transmitpaths of FIG. 2A.

FIG. 3 illustrates an embodiment of the receive side circuitryincorporating the spread spectrum calibration elements.

FIG. 4 is a block diagram for one embodiment of a calibration block.

FIG. 5 is a flow chart illustrating one embodiment for a receive sidecalibration operation using a spread spectrum, low power calibrationsignal.

FIG. 6 illustrates an embodiment of the transmit side circuitryincorporating the spread spectrum calibration elements.

FIG. 7 is a flow chart illustrating one embodiment for a transmit sidecalibration operation using a spread spectrum, low power calibrationsignal.

FIG. 8 is a schematic representation of a portion of the transmitsection of FIG. 6 to illustrate the mixing of channels.

FIG. 9 is a flow chart illustrating one embodiment for incorporating atwo-step calibration process into the transmit side flow of FIG. 5.

FIG. 10 is a flow chart illustrating one embodiment for basing thecalibration dwell time on the power level in a sub-channel.

FIG. 11 is an embodiment for receive side calibration elements using aprobe to inject the calibration signal.

FIG. 12 is an embodiment for transmit side calibration elements using aprobe to extract the propagated calibration signal.

FIG. 13 illustrates the drift in phase of two paths over time.

FIG. 14 is a block diagram of a 4×4 embodiment for a multiport amplifier(MPA).

FIG. 15 illustrates the different paths from one input of a multiportamplifier to one of its outputs.

FIG. 16 illustrates an embodiment of a multiport amplifier with avirtual input hybrid matrix and gain and phase equalizers.

FIG. 17 is a block diagram of a satellite or other beamforming apparatusthat incorporates a multiport amplifier with a virtual input hybridmatrix and gain and phase equalizers as in FIG. 16.

FIG. 18 looks at one embodiment for the MPA calibration block of FIG. 16in more detail.

FIG. 19 is a flow chart illustrating one embodiment for an MPAcalibration operation using a spread spectrum, low power calibrationsignal.

DETAILED DESCRIPTION

The following presents techniques allowing channels of a satellite to becalibrated while the channels are in active operation. A spread spectrumcalibration signal is generated and injected into a channel of thesatellite. The spread spectrum signal has a power level below thethermal noise floor of a customer or user signal active in the channel,allowing the calibration to be performed without disruption in service.After passing through a section of the channel, such as the receive ortransmit portion, the calibration signal is de-spread and used todetermine adjustments to calibrate the channel. Although the followingis described primarily in the context of a beamforming system, due tothe usually more stringent calibration requirements of such systems, thetechniques can also be applied more generally to non-beamformingsatellites and systems.

To further improve the calibration process, when the transmit side ofthe satellite includes an output hybrid matrix, the calibration of thetransmit side can be performed in two steps. In a first step, the spreadspectrum calibration signal is injected into the path at the input of anoutput hybrid matrix and used to calibrate this portion of the path. Asecond calibration step is then performed to correct for the whole ofthe channel's transmit path.

The efficiency of the calibration process can be improved by accountingfor the power of the user signal in a channel. The lower the power of achannel's signal, the lower the signal to noise ratio for that channel,so that the lower the power of the user's signal in the channel, theless time is spent calibrating the channel. Consequently, rather thanuse a calibration time based on the worst case (i.e., highest) powerthat may be planned in an active channel, the calibration time in eachcan be based on the actual power level of the user signal in thechannel.

To reduce circuit complexity and weight, rather than having theswitching and multiplexing circuitry to inject and extract the spreadspectrum calibration signal individually for each channel, a receiveantenna probe can concurrently inject the calibration into multiplechannels and a transmit antenna probe can concurrently extract thecalibration signal from multiple channels.

To reduce the frequency with which such calibrations need to beperformed, the signal paths can be calibrated based on relative path topath differences, rather than calibrating relative to some absolute baseline. As beamforming requires that the different signals for thesatellite have the proper amplitude, phase and delay relative to oneanother, if all of the signals have a common amount of drift forsignals, they will still form a beam. Consequently, by using a path topath calibration, the channels will not need to be calibrated for commonshifts in phase and other parameters.

The use of a spread spectrum calibration signal can also be applied tomultiport amplifiers (MPAs) when used in a satellite or more generallyto calibrate an MPA when in active operation. As in the beamformingdevice example, a spread spectrum calibration signal can be injectedinto the MPA and propagated through its different amplification paths.The propagated signals can then be compared to the original signal todetermine adjustments to the phase, gain and other parameters toequalize the different paths relative to one another so as to form awell-defined output signal from an input signal. Many of the techniquesused for the beamforming example can also be applied to MPA calibration.

FIG. 1 illustrate one embodiments in which these calibration methods canbe applied and depicts a block diagram of a wireless communicationssystem that includes a communication platform 100, which may be asatellite located, for example, at a geostationary or non-geostationaryorbital location. In other embodiments, other platforms may be used suchas UAV or balloon, or even a ship for submerged subscribers. In yetanother embodiment, the subscribers may be air vehicles and the platformmay be a ship or a truck where the “uplink” and “downlink” in thefollowing paragraphs are reversed in geometric relations. Platform 100may be communicatively coupled to at least one gateway 105 and aplurality of subscriber terminals ST (including subscriber terminals107). The term subscriber terminals may be used to refer to a singlesubscriber terminal or multiple subscriber terminals. A subscriberterminal is adapted for communication with the wireless communicationplatform including as satellite 100. Subscriber terminals may includefixed and mobile subscriber terminals including, but not limited to, acellular telephone, wireless handset, a wireless modem, a datatransceiver, a paging or position determination receiver, or mobileradio-telephone, or a headend of an isolated local network. A subscriberterminal may be hand-held, portable (including vehicle-mountedinstallations for cars, trucks, boats, trains, planes, etc.) or fixed asdesired. A subscriber terminal may be referred to as a wirelesscommunication device, a mobile station, a mobile wireless unit, a user,a subscriber, or a mobile.

In one embodiment, satellite 100 comprises a bus (i.e. spacecraft) andone or more payloads (i.e. the communication payload). The satellite mayalso include multiple power sources, such as batteries, solar panels,and one or more propulsion systems, for operating the bus and thepayload.

At least one gateway 105 may be coupled to a network 140 such as, forexample, the Internet, terrestrial public switched telephone network,mobile telephone network, or a private server network, etc. Gateway 105and the satellite (or platform) 100 communicate over a feeder beam 102,which has both a feeder uplink 102 u and a feeder downlink 102 d. In oneembodiment, feeder beam 102 is a spot beam to illuminate a region 104 onthe Earth's surface (or another surface). Gateway 105 is located inregion 104 and communicates with satellite 100 via feeder beam 102.Although a single gateway is shown, some implementations will includemany gateways, such as five, ten, or more. One embodiment includes onlyone gateway. Each gateway may utilize its own feeder beam, although morethan one gateway can be positioned within a feeder beam. Note that theterms “feeder” beams and “service” beams are used for convenience. Bothfeeder beams and service beams are spot beams and the terms are not usedin a manner to limit the function of any beam. In one embodiment, agateway is located in the same spot beam as subscriber terminals.

Subscriber terminals ST and satellite 100 communicate over servicebeams; for example, FIG. 1 shows service beams 106, 110, 114 and 118 forilluminating regions 108, 112, 116 and 120, respectively. In manyembodiments, the communication system will include more than fourservice beams (e.g., 60, 100, etc.). Each of the service beams have anuplink (106 u, 110 u, 114 u, 118 u) and a downlink (106 d, 110 d, 114 d,118 d) for communication between subscriber terminals ST and satellite100. Although FIG. 1 only shows two subscriber terminals within eachregion 108, 112, 116 and 120, a typical system may have thousands ofsubscriber terminals within each region.

In one embodiment, communication within the system of FIG. 1 follows anominal roundtrip direction whereby data is received by gateway 105 fromnetwork 140 (e.g., the Internet) and transmitted over the forward path101 to a set of subscriber terminals ST. In one example, communicationover the forward path 101 comprises transmitting the data from gateway105 to satellite 100 via uplink 102 u of feeder beam 102, through afirst signal path on satellite 100, and from satellite 100 to one ormore subscriber terminals ST via downlink 106 d of service beam 106.Although the above example mentions service beam 106, the example couldhave used other service beams.

Data can also be sent from the subscriber terminals ST over the returnpath 103 to gateway 105. In one example, communication over the returnpath comprises transmitting the data from a subscriber terminal (e.g.,subscriber terminal 107 in service beam 106) to satellite 100 via uplink106 u of service beam 106, through a second signal path on satellite100, and from satellite 100 to gateway 105 via downlink 102 d of feederbeam 102. Although the above example uses service beam 106, the examplecould have used any service beam.

FIG. 1 also shows a Network Control Center 130, which includes anantenna and modem for communicating with satellite 100, as well as oneor more processors and data storage units. Network Control Center 130provides commands to control and operate satellite 100. Network ControlCenter 130 may also provide commands to any of the gateways and/orsubscriber terminals.

In one embodiment, communication platform 100 implements the technologydescribed above. In other embodiments, the technology described above isimplemented on a different platform (e.g. on the ground or on adifferent type of satellite) in a different communication system.

The architecture of FIG. 1 is provided by way of example and notlimitation. Embodiments of the disclosed technology may be practicedusing numerous alternative implementations.

FIG. 2A is a block diagram of a satellite or other beamforming apparatusfor a simplified example of two input ports and two output ports,illustrating some of the elements that an embodiment of satellite 100 ofFIG. 1 may include. Although FIG. 2 shows only two input ports andpaths, and two output ports and paths for purposes of discussion, a realimplementation of a satellite 100 as in FIG. 1 may have tens or evenhundreds of such inputs, outputs and channels.

In this example, the receive side of the satellite 200 includes twoantennae or other input ports 201, 203 each connected to a correspondinginput path 205, 207. The input paths include low noise amplifiers (LNAs)and other low power equipment (LPE), such as mixers, amplifiers andfilters used to process the received signals, which are then separatedout into sub-channels, where the example shows two sub-channels perchannel. These elements can introduce relatively large phase, delay andgain variations, such as can be caused by temperature variations. In asatellite application, when power consumption is a major consideration,use of low power elements is important, but in other applications wheresuch constraints are less important, higher power components can beused. To account for gain, phase and other variations in each of thesub-channels on the receive side, a set of calibration correctionelements 243 a-d are included in the sub-channel receive paths. Thesecan be adjusted to calibrate the individual sub-channels, such as wouldbe done during an initial calibration process for the receive side.

On the transmit side, the two antennae or other output ports 221 and 223are supplied signals from the output block 220. Output block 220includes transmit path 1 circuitry 225 and transmit path 2 circuitry227, which each include mixers, filters and amplifiers, including thehigh-powered amplifiers at the end, to generate the signals for theoutput ports 221 and 223. The transmit path 1 circuitry 225 and transmitpath 2 circuitry 227 is connected to the output ports 221 and 223through output hybrid matrix OHM 228 on the one side and to the inputhybrid matrix IHM 229 on the input side. The input hybrid matrix IHM 229allows for a signal from any one of the sub-channels to be distributedacross multiple transmit paths, and the output hybrid matrix OHM 228allows signals from any of the transmit paths to be directed to any ofthe output ports. Rather having all transmit paths be able to handle themaximum amplification power that may be needed in a single channel, theuse of the input hybrid matrix IHM 229 and the input hybrid matrix IHM229 allows for the signal of a sub-channel to be distributed acrossmultiple transmit paths so that unused amplification power inunderutilized channels is used to supply extra power for sub-channelsneeding higher degrees of amplification. This division of amplificationallows for the individual transmit paths to use amplifiers of lowerpower, and consequently less cost and lower weight, which is animportant concern in a satellite. A set of calibration pre-correctionelements 245 a-d are included in the sub-channel paths are included toaccount for gain, phase and other variations in each of the transmitsub-channels on the transmit side. These can be adjusted to calibratethe individual transmit sub-channels, such as would be done during aninitial calibration process for the receive side.

A digital channelizer section 240 connects the receive side and thetransmit side. In addition to the correction elements 243 a-d for thereceive sub-channels and the pre-correction elements 245 a-d for thetransmit sub-channels, multiplexing circuitry MUX 241 selectivelyconnects the receive sub-channels and the transmit sub-channels.

FIGS. 2B and 2C provide more detail on the receive paths and transmitpaths of FIG. 2A. FIG. 2B is block diagram illustrating an embodiment ofa receive path block, such as 205 or 207 in FIG. 2A, in more detail.More specifically, FIG. 2B provides more detail on some of the elementsof one embodiment of receive path 1 205, where other receive paths wouldhave a similar structure. The signal from the input port, such as anantenna 201, is initially received at a low noise amplifier 261. Theamplified input signal is then filtered at block 263, down-convertedfrom the received RF range to an intermediate frequency at block atblock 265, before being filtered again at block 267. The signal is thensent on to the digital processing elements of the channelizer section240 and separated out into sub-channels. The calibration process willallow the gain, phase and delay variations across the receive path to bedetermined.

FIG. 2C provides more detail on some of the elements of one embodimentof the transmit path 1 225 as connected between the input hybrid matrixIHM 229 and the output hybrid matrix 228, where other transmit pathswould have a similar structure. The signal from the input hybrid matrixIHM 229 is filtered at block 271 and then up-converted from the IF rangeto the RF range in block 273, before being filtered again at block 275.The filtered and up-converted signals are then amplified initially by alow power amplifier 278 and then a high-power amplifier 279, beforegoing on to the output hybrid matrix OHM 228. The input hybrid matrixIHM 229 and output hybrid matrix OHM 228 allow for different signals tobe distributed across multiple high-power amplifiers from differentpaths to provide higher amounts of power for a signal than availablefrom a single path, but without the need to have each path to be able tothe worst case maximum amplification all by itself.

As noted above, the satellite 200 includes a set of calibrationcorrection elements 243 a-d in the sub-channel receive paths andcalibration pre-correction elements 245 a-d for the sub-channel transmitpaths. These can be used for an initial calibration process prior to thesatellite being put into service. However, once the satellite is inservice, a channel's calibration traditionally cannot be updated whilein use without disruption of any active user signals. Freeing up pathsor sub-channels to allow measurement of gain, phase, delay or othervalues for calibration is not practical during active operation of thesatellite payload. The following describes the use of spread spectrumcalibration waveforms with power levels below the noise floor of theactive signals, allowing calibration to be performed during activeoperation of the payload.

Although more generally applicable, the techniques described here areparticularly useful for beamforming satellites, since in order to form abeam these are calibrated to a set of requirements that are tighter thatthose for a non-beamforming satellite. Having methods that measure gain,phase, and delay stability in an effective manner combine to reducecomplexity and cost, allowing the payload hardware specification ofgain, phase and delay stability to be more relaxed. The embodimentsprimarily described below allow the receive paths and the transmit pathsto be individually calibrated. They also allow the simultaneouscalibration of the transmit paths before and after an output hybridmatrix and can be done in a time effective manner for satellites withmany channels.

Making periodic calibrations during the active operation of channels canhelp allow the payload hardware specification of gain, phase and delaystability to be more relaxed (for example, relaxing the gain variationspecification from 0.2 dB to 10 dB for path to path differences), whichcan lead to saving in cost. Embodiments described here use a spreadspectrum calibration signal generated from a pseudo-random noisesequence that can reside, for example, in a 1 MHz sub channel and set toa power level below the thermal noise floor (such as 17 dB below) at theinput to the receive antenna elements to calibrate the receive path orat the input to the transmit paths to calibrate the transmit path. Thepseudo random code known by the source and the receiver and used torecover the calibration signal information from an active channelsignal. The calibration signal is a DC signal and the pseudo randomcode's spectrum (bandwidth) is wider than the calibration signal'sInformation bandwidth. The calibration signal can be injected into thesignal path any time a measurement is desired, without interference touser signals. After passing through a particular receive or transmitpath, the signal is de-spread, raising it above the other signal energyin the sub channel, where it is detected and measurements can be made todetermine adjustments to be used in the calibration.

FIG. 3 illustrates an embodiment of the receive side circuitryincorporating the spread spectrum calibration elements, repeating thereceive side elements of FIG. 2 and adding calibration elements. Morespecifically, the receive side of the satellite includes two antennae orother input ports 301, 303 each connected to a corresponding input path305, 307. A set of calibration correction elements 343 a-d are includedin the sub-channel receive paths.

A calibration block 350 is connected to receive a local referencesignal, from which it generates a calibration signal. In thisembodiment, the calibration signal is a low power spread spectrum signalformed from pseudo-random noise at an intermediate frequency of 1080MHz. A calibration up-converter block 351 up-coverts the calibrationsignal up to the RF range of, in this example, 27-30 GHz. Theup-converter block 351 can also include filters and amplifiers toincrease the gain, according to the embodiment. A calibration injectionports 352 a and 352 b allow the calibration signal to be selectivelyinjected at the start of path 1 305 and path 2 307, respectively.Multiplying the received signal (combination of the active channel plusthe calibration signal) by a local version of the pseudo random codereduces the calibration signal bandwidth (which is the pseudo randomcode bandwidth, i.e. a wideband signal) to the calibration signal'sinformation bandwidth (narrowband). Multiplying the received signal(combination of the active channel plus the calibration signal) by alocal version of the pseudo random code increases the active channelbandwidth by the calibration signal's bandwidth. After propagatingthough a selected path and sub-channel, the injected calibration signalis extracted at extraction ports 344 a-d and received back at thecalibration block, where it can be de-spread and compared with theoriginal signal. Based on the comparison, update corrections can bedetermined and supplied to the calibration correction elements 343 a-d.Depending on the embodiment, based on the comparison the corrections canbe determined on the satellite, on the ground, or some combination ofthese. In FIG. 3, the calibration can be between sub channels in thechannelizer 340. This is because calibration will not only measurevariation between paths, but also variation between sub channels. Ineffect this is measuring variation across frequency and will be used forequalization across frequency when needed.

Using correlation, the pseudo random code spread active channel signalcan separated from the calibration signal's information. The embodimentspresented here use coding to recover the calibration signal from theactive channel signal, rather than using frequency filtering to isolatethe calibration signal from the active channel signal. Both thecalibration block 350 and up-converter 351 can be implemented as variouscombinations of one or more of hardware, software and firmware,depending on the embodiment. In the illustrated embodiment, the samecalibration block is used for both receive side calibration and transmitside calibration (FIG. 6, below), but in other embodiments the transmitside can have separate calibration elements from the receive side.Additionally, although shown as part of the digital channelizer block340 in the shown embodiments, more generally part or all of thecalibration block elements can be incorporated into other parts of thesatellite.

FIG. 4 is a block diagram for one embodiment of a calibration block 450,such as can be used for calibration block 350 in FIG. 3 or calibrationblock 650 in FIG. 6 below. Block 451 receives a local time reference andfrom this generates the spread spectrum calibration signal, which thenhas its power level adjusted at block 453, providing the spread signal,low power calibration signal for injection. For the receive path, thissignal is first up-converted, as illustrated in FIG. 3. Afterpropagating through a portion of the circuitry, the calibration signalis then received at the multiplier 459, where it is combined with theoriginal calibration waveform, the result going to thecorrelation/accumulation block 454. From the correlated, accumulatedvalues, update corrections are then determined at block 455. Thecorrection values can be used to determine gain/phase/delay values basedon stored values, such as a look up table, at block 456, which are inturn used to update the calibrations for the sub-channels. The scheduler457 determines which sub-channel is to be calibrated and when.

FIG. 5 is a flow chart illustrating one embodiment for a receive sidecalibration operation using a spread spectrum, low power calibrationsignal as described with respect to FIGS. 3 and 4. The use of the spreadspectrum, low power calibration signal allows for a calibrationoperation to be performed on an active channel, although the calibrationoperation can also be performed when a channel is otherwise not active,such as part of a test mode. FIG. 5 describes a receive side calibrationoperation in an active path. At step 501, the satellite receives a usersignal at an antenna and, from this received signal, generates one ormore corresponding output signals at step 503. In the beamformingexample, multiple output signals are formed so that a beam is formedwhen these are transmitted from corresponding multiple transmitantennae. At step 505, the output signals are transmitted. Step 510 isthe calibration process and can be performed concurrently with thegenerating of the output signals by the beamforming circuitry at step503.

The flow for the calibration operation of step 510 begins at step 511with a locally generated reference signal, such as a pseudo-random noisesignal generated on the satellite. At step 513 the spread spectrumcalibration signal is then generated from the pseudo-random noisesequence and in one embodiment can reside in a 1 MHz sub channel and setto a power level below the thermal noise floor (such as 17 dB below) ofthe user signals in the channel. At step 515 the calibration signal isup-converted into, for example the 27-30 GHz range and, at step 517,injected into a selected receive path or portion of a receive path. Thecalibration for different paths and sub-channels can be performedsequentially according to a schedule based on how quickly thecalibration of the different channels are found to drift. The injectedcalibration signal is then propagated through selected sub-channels ofthe receive side of the beamforming circuitry at step 519. Although themain embodiments presented here calibrate receive side and transmit sideseparately, alternate embodiments can calibrate the combined receive andtransmit paths in a single process or, conversely, further divide up thecircuitry in to smaller sections for calibration.

After the injected signal propagate the selected path, it is receivedback at the calibration block at step 521 and de-spread at step 523. Thede-spread signal can then be compared to the original reference signalat step 525 and, based on the comparison the updates needed for thecalibration values of the sub-channel can be determined at step 527.Depending on the embodiment, the determination of the update correctionscan be performed by processing circuitry on the satellite; determined onthe ground based on the results of the comparison sent by the satellite,with the results then returned to the satellite; or a combination ofthese. It should again be noted that although embodiments shown in thefigures here show only two paths, in an actual satellite the number ofchannels can run into the tens or even hundreds. The update correctionsare then applied to the calibration correction elements 343 a-d of thesub-paths at step 529.

The calibration of delay, phase and gain values can be made relative tofixed normative values or, as discussed more below with respect to FIG.13, based on the differential variation in delay, gain, and phasebetween paths 1 and 2. Except for the RF probe introduced below withrespect to FIG. 11, the calibration loop is common mode and will notvary between the times it takes to measure the different paths in thefront end. A comparison of the signal through the loop and along each ofthe front-end paths against a local reference allows the system toestimate the difference between any two paths and hence calibrate itout.

In the calibration process, the phase adjustment to each path can bemade after the comparison to the local reference. A timing adjustmentcan be performed first, after which a residual delay may remain. Thephase of each path can be measured relative to the local reference suchthat paths are coherent at radio frequencies. The local reference can beadjusted to minimize the largest required correction across all paths.The gain adjustment of each path can be to a local nominal value, whichcan slowly adjust to minimize the largest required correction across allpaths.

Looking now at the transmit side calibration, the transmit sidecalibration is concerned with measuring the variations in delay, gain,and phase in transmit path 1 circuitry 225 and transmit path 2 circuitry227 of FIG. 2A, as well as in the input hybrid matrix IHM 229 and outputhybrid matrix OHM 228. As with the receive side, the rest of thecalibration loop is common mode or measured beforehand and accounted forin the calibration. One difference from the receive side is theexistence of the hybrid matrices IHM 229 and OHM 228. As these mixsignals from multiple paths, these can have their own gain/phasematching problems. As discussed further below with respect to FIG. 8, insome embodiments the transmit side calibration can be done in two stepsto account for these elements.

FIG. 6 illustrates an embodiment of the transmit side circuitryincorporating the spread spectrum calibration elements, repeating thetransmit side elements of FIG. 2 and adding calibration elements. Morespecifically, the transmit side of the satellite includes two antennaeor output ports 621 and 623 each connected to a corresponding transmitpath 625, 627 through the output hybrid matrix OHM 628. A setcalibration pre-correction elements 645 a-d are included at the start ofthe sub-channel transmit paths. Signals from the sub-channels in thedigital channelizer section 640 connected to the transmit paths 625 and627 by the input hybrid matrix IHM 629.

The calibration block 650 is connected to receive a local referencesignal, from which it generates a calibration signal. As with thereceive side embodiments described with respect to FIGS. 3-5, in thisembodiment, the calibration block 650 generates a calibration signalthat is a low power, spread spectrum signal formed from pseudo-randomnoise. In the embodiment illustrated in FIG. 6, the calibration signalis injected at injection ports 655 a-d into selected sub-channels beforethe pre-correction elements 645 a-d and extracted at before the outputports 621 and 623 at the calibration extraction ports 654 a and 654 b.In other embodiments, the calibration signal can be injected, extractedor both at other points in order calibrate smaller divisions of thetransmit circuitry. A calibration down-converter 653 down-converts theextracted RF frequency calibration signal to an intermediate frequency(1080 MHz in this example) and returns it to the calibration block 650,where it can be de-spread and compared with the original signal. Basedon the comparison, update corrections can be determined and supplied tothe pre-calibration correction elements 645 a-d. The determination ofthe pre-correction updates from the comparisons can performed on thesatellite, on the ground, or a mixture of these.

FIG. 7 is a flow chart illustrating one embodiment for a transmit sidecalibration operation using a spread spectrum, low power calibrationsignal as described with respect to FIG. 6. The use of the spreadspectrum, low power calibration signal allows for a calibrationoperation to be performed on an active channel, although the calibrationoperation can also be performed when a channel is otherwise not active,such as part of a test mode. FIG. 7 describes a receive side calibrationoperation in an active path. At step 701, the satellite receives a usersignal at an antenna and, from this received signal, generates one ormore corresponding output signals at step 703. In the beamformingexample, multiple output signals are formed so that a beam is formedwhen these are transmitted from corresponding multiple transmitantennae. At step 705, the output signals are transmitted. Step 710 isthe calibration process and can be performed concurrently with thegenerating of the output signals by the beamforming circuitry at step703.

The flow for the calibration operation of step 710 begins at step 711with a locally generated reference signal, such as a pseudo-random noisesignal generated on the satellite. At step 713 the spread spectrumcalibration signal is generated from the pseudo-random noise sequenceand in one embodiment can reside in a 1 MHz sub channel and set to apower level below the thermal noise floor (such as 17 dB below) of theuser signals in channel. At step 715 the calibration signal is injectedinto a selected transmit path sub-channel. The calibration for differentpaths and sub-channels can be performed sequentially according to aschedule based on how quickly the calibration of the different channelsare found to drift. The injected calibration signal is then propagatedthrough selected sub-channels of the transmit side of the beamformingcircuitry at step 717. Although the main embodiments presented herecalibrate receive side and transmit side separately, alternateembodiments can calibrate the combined receive and transmit paths in asingle process or, conversely, further divide up the circuitry in tosmaller sections for calibration.

After the injected signal propagates through the selected path, it isextracted and down-converted at step 719, received back at thecalibration block at step 721 and de-spread at step 723. The de-spreadsignal can then be compared to the original reference signal at step 725and, based on the comparison the updates needed for the pre-calibrationvalues of the sub-channel can be determined at step 727. Depending onthe embodiment, the determination of the update corrections can beperformed by processing circuitry on the satellite; determined on theground based on the results of the comparison sent by the satellite,with the results then returned to the satellite; or a combination ofthese. It should again be noted that although embodiments shown in thefigures here show only two paths, in an actual satellite the number ofchannels can run into the tens or even hundreds. The update correctionsare then applied to the calibration correction elements 645 a-d of thesub-paths at step 729.

In FIG. 6, the calibration signal is injected before the input hybridmatrix IHM 629 and extracted after the output hybrid matrix OHM 628, sothat phase, gain and delay errors can be introduced in any of theseelements, as well as in any amplifiers or other elements in the transmitpaths 625 and 627. Consequently, these transmit side differs from thefrom the receive side due to the complication of the hybrid matrices IHM229 and OHM 228.

FIG. 8 is a schematic representation of this portion of the transmitsection of FIG. 6 to illustrate the mixing of channels. As shown atleft, both channels are input into the input hybrid matrix IHM 829,which allows the signal from either channel to be distributed acrossboth of transmit track path 1 825 and transmit path 2 827, so that theamplifiers in both paths can be used for a given signal. The outputhybrid matrix OHM 828 allows the output from either, or both, oftransmit path 1 825 and transmit path 2 827 to be directed to either ofthe output ports 821 and 823. As these hybrid matrices mix signals frommultiple paths, these elements can have their own gain and phasematching problems. To account for this, in some embodiments the transmitside calibration can be done in multiple steps.

For example, in a first calibration phase, the calibration signal can beinjected at the injection ports 858 a and 858 b, before the outputhybrid matrix OHM 828 and the circuitry of the transmit paths 825 and827, but after the input hybrid matrix IHM 829. If the multiplexingcircuitry of the output hybrid matrix OHM 828 is balanced, there will bea known gain at the calibration extraction ports 854 a and 854 b. Afterupdating the calibration for these elements, the calibration for thewhole of the transmit side can be performed assuming that the outputhybrid matrix OHM 828 introduces no error. The process of measuring thecalibration parameters for the output hybrid matrix and then correctingfor the full path can be iterated if desired to increase the calibrationaccuracy.

FIG. 9 is a flow chart illustrating one embodiment for incorporating atwo-step calibration process into the transmit side flow of FIG. 7,where an initial calibration is done for a hybrid matrix elementfollowed by a full transmit side calibration. Referring back to FIG. 7,after step 705, the transmit path of FIG. 6 is calibrated at step 710,where the calibration signal is injected before the input hybrid matrixIHM 629 of FIG. 6 and extracted after the output hybrid matrix OHM 628.In FIG. 9, the calibration step 710 is performed twice, a first time atstep 710 a where the calibration signal is injected at a selected one of858 a and 858 b, with steps 711-729 performed for the output hybridmatrix 828 section and the circuitry of the transmit paths 825 and 827.Step 710 b is then performed a second time, performing steps 711-729 forthe whole of the transmit path. If higher accuracy is wanted, theprocess can be iterated by looping back at step 730 to repeat step 710a.

To simplify the discussion, the examples illustrated here have beenusing only two receive paths and two transmit paths, but an actualsatellite may have tens or even hundreds of such paths. Consequently,even if a calibration operation of a signal sub-channel or path does notrequire an overly large amount of time, measuring the gain, phase anddelay for all or most paths and frequencies to the required accuraciesfor beamforming can be time consuming.

The amount of time required to accurately measure the amount of error ina sub-channel depends on the signal to noise ratio (S/N) for the usersignal active in a path. To be able to accurately measure the error in apath for all power levels with a fixed integration or dwell time wouldrequire that all measurements assume the highest power level that may beused in a channel. However, by reducing the dwell time for eachmeasurement based on the actual power level in each path/sub channel,the system can reduce the load on the circuitry and processing by largefactors (such as 10-100 based on maximum to minimum user power level ineach sub channel).

Each path/sub channel has a power level estimate associated with it,based on the user signal active in it. The lower the power of thesignal, the lower the S/N value. The dwell time for measurement fordetermining the error in a path can be made a function of the power,with less time spend on lower power sub-channels and only the mostpowerful signals requiring the maximum dwell. As one of the measurementsmade in the calibration process is gain, this can be used to update thepower level estimate associated with the path/sub channel, which in turncan be used to determine a dwell time.

FIG. 10 is a flow chart illustrating one embodiment for basing thecalibration dwell time on the power level in a sub-channel. For a givensub-channel, the dwell time determination can be inserted between steps505 and 510 for a receive side calibration and between steps 705 and710. At step 507/707, the power of the user signal active in thesub-channel at step 503/703 is determined. Based on this power level,the dwell time for the calibration is determined at step 509/709, afterwhich the calibration is performed at step 510/710 using this dwelltime.

As illustrated in the embodiment of FIG. 3, the calibration signal isinjected into the different paths through the calibration injectionports 352 a and 352 b. Similarly, in the embodiment of FIG. 6, thecalibration signals are extracted at the calibration extraction ports654 a and 654 b. Introducing the switching and taps for the calibrationinjection ports in the receive paths and calibration extraction ports inthe transmit paths of a beamforming satellite to inject and retrievecalibration signals is expensive in complexity and weight of the payloadas actual satellites can have large numbers of such paths. Using atransmit probe to inject power into all elements of the receive antennaand a receive probe to collect power from all elements of the transmitantenna can be much simpler and have lower weight.

FIG. 11 is an embodiment for receive side calibration elements using aprobe to inject the calibration signal. FIG. 11 repeats many of theelements of FIG. 3, including two antennae or other input ports 1101,1103 each connected to a corresponding input path 305, 307. A set ofcalibration correction elements 1143 a-d are included in the sub-channelreceive paths in the digital channelization section 1140. Thecalibration block 1150 operates as described with respect to FIGS. 3 and4, including generating the IF calibration signal that is up-convertedat block 1151 to the RF range. Rather than inject the up-convertedcalibration signal into each of the individual paths as in FIG. 3, aprobe 1191 is introduced at the receive antenna to emit energy into thereceive elements. This removes the need for the switching and tapelements for each of the paths as the calibration signal is nowtransmitted into all receive paths at the same time. The individualpaths can then be selected and calibrated as described above withrespect to FIG. 5.

FIG. 12 is an embodiment for transmit side calibration elements using aprobe to extract the propagated calibration signal. FIG. 12 repeats manyof the elements of FIG. 6, including the two antennae or other outputports 1221 and 1223 supplied signals from the output block 1220. Outputblock 1220 includes transmit path 1 circuitry 1225 and transmit path 2circuitry 1227, hybrid matrix OHM 1228 and input hybrid matrix IHM 1229.The propagated calibration signal is down-converted at block 1253 andreturned to the calibration block 1250, which injects the calibrationsignal into the sub-channels in the digital channelization section 1240.Rather than extract the calibration signal from each of the individualpaths as in FIG. 6, a probe 1293 is introduced at the transmit antennato collect energy from the transmit elements. The antenna 1221, 1223transmit the signals to form each of the beams to the ground, part ofwhich is picked up by the probe 1293. This removes the need for theswitching and tap elements to extract the calibration signalindividually from each of the paths, as the calibration signal can nowbe extracted from the signals received from all transmit paths by thesame probe 1293. The individual paths can then be calibrated asdescribed above with respect to FIG. 7.

For both the receive probe and transmit probe, the coupling from theprobes to the elements can be characterized as part of the initialtesting and calibration of the system. As with the previously describedembodiments, the calibration signal is recovered by knowing thespreading code and pulling the signal out of the noise. Except for theprobe portions, the rest of the calibration loop can be common mode andwill not vary between the times it takes to measure the different paths.A comparison of the signal through a loop and along each of the transmitor receive paths is checked against the local reference as describedabove, allowing the system to estimate the difference between any twopaths and calibrate it out. The variation in the probe segments can becalculated and/or measured beforehand and accounted for in thecalibration. Most of the variation will typically be in the amplifiersand low power equipment (LPE) for the paths.

When drift rates for phase, gain, and delay are high, sample calibrationmeasurements will have to be performed relatively frequently.Calibrating these parameters by measuring the gain, phase and delay ofeach path to fixed internal reference values can imposes an unnecessaryspecification on absolute drift rates. In a beamforming system, it isthe relative path-to-path differences in the signals, rather that theabsolute values, that are more important since if, for example, a set ofbeamforming signals are all out of phase, but out of phase by the sameamount, they will still form a beam. Calibrating the path-to-pathdifferences in gain, phase and delay of pairs of paths can relax thespecification on absolute drift rates. The use of a Kalman filter, forexample, allows for path-to-path calibration. FIG. 13 illustrates thesituation.

FIG. 13 illustrates the drift in phase of two paths over time. Forexample, φ₁(t) and φ₂(t) could be the phase for paths 1 and 2 for eitherthe receive side of FIG. 3 or the transmit side of FIG. 6. Initially,φ₁(t) and φ₂(t) are calibrated to an absolute phase φ₀, but over timedrift. If this rate of drift is fast, the phase calibration would needto be performed frequently. However, both of φ₁(t) and φ₂(t) may bedrifting in a similar manner, such as due to, for example, temperaturevariations that affect both paths similarly. Consequently, although bothof φ₁(t) and φ₂(t) may differ significantly from an absolute phase φ₀,the path-to-path difference between them may still be close enough toeach other to form a beam. The line φ′₀(t) is an average amount of driftfor φ₁(t) and φ₂(t) and can instead be used as the basis for determiningthe calibration and how often to calibrate. In FIG. 13, φ′₀(t) is astraight line, but it can also be non-linear when the averaged driftrate varies over time.

The calibrating of path-to-path differences can utilize a Kalman filter,where the internal state is the difference between a calibrationparameter and a mean for that parameter. The observables are theindividual measurements against an internal reference, where transientsof the sample rate are lower than the dynamics of the parameters. TheKalman estimator can smoothly track the internal state and allowcorrection of the path-to-path variation with tracking of the absolutedrift.

The above discussion focused on the calibration of the signal paths in asatellite such that the signals from the output ports or antennae form abeam when transmitted. To do this, the signals from the different outputports need to be sufficiently well calibrated with respect to oneanother so that they are beamforming when incident on the desiredlocation. Referring back to FIG. 2A, the techniques described abovecalibrate various portions of the paths between the input ports orantennae 201, 203 and the output ports or antennae 221, 223 so that thesignals transmitted form output ports 221, 223 are calibrated wellenough relative to one to form a beam. A section of the paths betweenthe input ports 201, 203 and the output ports 221, 223 is the outputblock 220.

Output block 220 includes the two paths, transmit path 1 circuitry 225and transmit path 2 circuitry 227. Each of these paths can includeelements such as mixers, filters and amplifiers, including thehigh-powered amplifiers at the end, to generate the signals for theoutput ports 221 and 223. The transmit path 1 circuitry 225 and transmitpath 2 circuitry 227 are both connected to the output ports 221 and 223through output hybrid matrix OHM 228 on the one side and to the inputhybrid matrix IHM 229 on the input side. The input hybrid matrix IHM 229allows for a signal from any one of the sub-channels to be distributedacross multiple transmit paths, and the output hybrid matrix OHM 228allows signals from any of the transmit paths to be directed to any ofthe output ports. This is an example of a 2×2 multiport amplifier (MPA).

Rather than having each path of an MPA individually be able to handlethe maximum amplification power that may be needed in a single channel,the use of the input hybrid matrix IHM 229 and the output hybrid matrixOHM 2299 in an MPA allows for the signal to be distributed across theamplification of multiple paths so that unused amplification power inunderutilized channels can be used to supply extra power for pathsneeding higher degrees of amplification. This division of amplificationallows for the individual transmit paths to use amplifiers of lowerpower, and consequently less cost and lower weight, which is animportant concern in satellites and many other applications.

When a signal from one input to the of the input hybrid matrix IHM 229is distributed across multiple amplification paths and then recombinedin the output hybrid matrix OHM 228 for a single output of OHM 228,these signals from the different paths should be relatively wellcalibrated (as far as phase, gain, etc.) with respect to one another inorder to properly reform the amplified signal from its components. Thisis a similar to the problem for beamforming satellite, except that inthat case the signals from the output ports 221, 223 needed to becalibrated with respect to one another to form a beam, while in thiscase the different paths leading each output of the output hybrid matrixneed to calibrated with respect to each other to properly produce thesignal at each of the individual outputs of the output hybrid matrix OHM228. (That is, rather than look at the how the signals from thedifferent output ports 221, 223 will combine as a beam, the calibrationof the MPA will look at each of the individual signals from the MPAbefore supplied to the respective output ports.) So although the pointat which the combination of different paths need to be well-calibratedwith respect to one another differs between beamforming and MPAcalibration, the similarities of the processes allow for many of thetechniques described above for a beaming forming system to be applied tomultiport amplifiers.

More specifically, the following looks at multiport amplifier (MPA)input networks with compensation for MPA output network gain and phasefrequency response imbalances, primarily for embodiments where the inputnetworks are implemented in digital signal processing. In addition tosatellites, MPAs can also be used in other amplification applicationsthat can benefit from the flexibility to move power from one outputchannel to another, as they allow the aggregate MPA power to be sharedamongst several beams or ports. The use of MPAs allows reconfiguring theoutput power among the different output channels in order to handleunexpected traffic imbalances and traffic variations over time. An MPArelies on parallel amplification of the signals by a group of poweramplifiers with controlled or matched gain and phase responses vsfrequency over time and temperature. At a basic level, an MPA includesan input hybrid matrix, a parallel group of amplifiers, and an outputhybrid matrix, where FIG. 14 illustrates an example 4×4 MPA.

FIG. 14 illustrates one example of an MPA, such as can be used at outputblock 220 of FIG. 2A or in other applications, here in a 4×4 embodimentsof four input ports and four output ports. The four input ports of theMPA are the four inputs of the input hybrid matrix 1401. In thisembodiment, the input hybrid matrix 1401 is a “virtual” input hybridmatrix as it is implemented digitally, as is discussed more below, butthis need not be the case in other embodiments. The four outputs of theMPA are the four outputs of the output hybrid matrix 1411. The fouroutputs of the input hybrid matrix 1401 are connected to the four inputsalong four amplification paths. The amplification paths can be similarto those described above with respect to FIG. 2C or other embodiments,but for this discussion each of the four paths are simplified to show ahigh-power amplifier HPA 1409 and a Gain & Phase Response block 1407.The high-power amplifiers HPA 1-4 1409 a-d are treated as idealamplifiers and any other elements in the paths between the input hybridmatrix 1401 and output hybrid matrix 1411 are grouped into Gain & PhaseResponse 1-4 1407 a-d and will include any phase or gain variation inthe corresponding path.

For example, the Gain & Phase Response 1-4 1407 a-d can represent gain,phase, delay or other response errors that arise in the various stagesof the paths for the MPA. Depending on the embodiment, these stages caninclude up-conversion from IF to RF, filters, low power amplification,digital to analog conversion, and so on. Although the high-poweramplifiers are represented in FIG. 14 as elements HPA 1-4 1409 a-d, asnoted above these are treated as ideal and any path variation ornon-ideal behavior from these is considered as part of the Gain & PhaseResponse blocks 1407 a-d.

FIG. 15 considers the paths from one input of an MPA, such asillustrated in FIG. 14 except for a generalized n×n embodiment, to oneof its outputs. In the simplified illustration of FIG. 15, an inputsignal S is received at an input port (input port n), distributed by theinput hybrid matrix to the n paths, and is amplified by n amplificationunits HPA1-HPAn of amplification block 1409 in parallel (input hybridmatrix 1401 and output hybrid matrix 1411 are omitted for simplicity).Signal S is split into signals S′ that travel along parallel pathwaysthrough gain and phase response stage blocks 1407 and amplificationstages 1409, with each pathway having a gain, phase and delay responsestage and an amplification unit. Thus, each pathway passes through adifferent gain and phase response stage. The amplified signals S″ arethen recombined and provided as an amplified output S at output port 1.FIG. 15 illustrates one input signal being distributed across all of theamplification pathways, but depending on the needed power and othersignals concurrently in the MPA from other ports, a given input signalwill be distributed across a subset of from 1 to all n of theamplification paths.

Depending on the embodiment, a calibration process can send thecalibration signals along paths from one input to one output at a time,or propagate the calibration signals between multiple input and outputports concurrently. For example, spread spectrum calibration signalscould be injected into multiple input ports concurrently, but withdiffering phases so that they may more easily be distinguished at theoutputs. (In the 4×4 case, for example, the calibration signal at thefour inputs could have phases of 0°, 90°, 180° and 270°.) Similarly, thecalibration can be done for a single frequency bin at a time, orconcurrently for multiple frequency bins.

Each of the paths between an input port and an output port passesthrough a different gain and phase response block. Because of this,although the signals S′ may all be aligned in phase and gain, each ofthe signals S″ may have acquired a difference in gain, phase, delay orother parameters relative to one another. Additional differences mayalso be introduced in input and output hybrid matrices. In order thatthe signals S″ when recombined to properly reform to provide S at output1 as an amplified version of S at input n, the gain, phase and delayalong these paths should be equalized relative to one another.

To determine the compensation values for the MPA, the spread spectrumtechniques similar to those described above for beam-forming systems canbe applied to MPAs. By making periodic calibrations during activeoperation (such as on-orbit when an MPA is used in a satellite) ofchannels allows the MPAs specification of gain, phase and delaystability to be more relaxed, saving cost (for example, relaxing thepath to path gain variation specification from 0.2 dB to 10 dB).Although the compensation circuitry can be implemented in both analogand digital embodiments, the discussion below is mainly given in thecontext of a digital implementation. Implementing the gain, phase anddelay compensation circuitry within a programmable digitalimplementation supports adaptive corrective action compensating payloadhardware gain, phase and delay variation vs time and temperature.Implementing the input hybrid matrix within a programmable digitalimplementation (a “virtual” input hybrid matrix) supports adaptivecorrective action compensating for gain and phase errors within theoutput hybrid matrix vs frequency due to aging and temperaturevariations. This leads to lower costs and improved MPA performance, suchas port-to-port isolation. Overall, this can help to reduce throughlower complexity, lower weight, and reduce testing time.

Consequently, each output of output hybrid matrix is a summation of aportion of the input signal from each output of the input hybrid matrixtimes a unique gain and phase coefficient associated with the differentpaths from an input port of the input hybrid matrix to an output port ofthe output hybrid matrix. Although for an ideal output hybrid matrix theinput hybrid matrix coefficients may be known and fixed, this will notbe the case. For real world output hybrid matrix implementations, theoptimum multiport amplifier performance is achieved when the inputhybrid matrix coefficients can be updated in order to compensate thenon-ideal real-world output hybrid matrix gain and phase coefficients.

The embodiments descried here present an equalizer within the virtualinput hybrid matrix that is able to adjust while in operation (on-orbit,for a satellite), in active channels the gain and phase versus frequencyresponse for each virtual input hybrid matrix output. Having the abilityto set the equalizer's gain and phase values under software commandallows the virtual input hybrid matrix, through its equalizer, toadaptively compensate the gain and phase frequency response of the MPA.This can be illustrated with the embodiment of FIG. 16.

FIG. 16 illustrates an embodiment of a multiport amplifier with virtualinput hybrid matrix and gain and phase equalizers. FIG. 16 illustrates a4×4 embodiment as in FIG. 14 and repeats many of the elements of FIG.14, where it will be understood that other embodiments can have more orless input and output ports. The four input ports of the MPA are thefour inputs of the input hybrid matrix 1601. The four outputs of the MPAare the four outputs of the output hybrid matrix 1611. The four outputsof the input hybrid matrix 1601 are connected to the four inputs alongfour amplification paths. The amplification paths can again be similarto those described above with respect to FIG. 2C, but as in FIG. 14 eachof the four paths are simplified to show a high-power amplifier HPA 1609and a Gain & Phase Response block 1607. The high-power amplifiers HPA1-4 1609 a-d are treated as ideal amplifiers and any other elements inthe paths between the input hybrid matrix 1601 and output hybrid matrix1611 are grouped into Gain & Phase Response 1-4 1607 a-d and willaccount for any phase or gain variation along the path. To compensatefor the path to path variations, each path also now includes a Gain &Phase Equalizer block 1603, where each of 1603 a-d can be used toequalize any path to path variations in gain, phase, delay or otherfactors from the corresponding one of the response blocks 1607 a-d.

In this embodiment, the input hybrid matrix 1601 is a “virtual” inputhybrid matrix as in is implemented digitally, but this need not be thecase in other embodiments. More specifically, the virtual input hybridmatrix 1601 and the gain and phase equalizer blocks 1-4 1603 a-d arepart of a virtual input hybrid matrix with equalization 1629. Whenimplemented in a satellite embodiment as in FIG. 2A, the virtual inputhybrid matrix with equalization 1629 can be part of the digitalchannelizer processor block 240. The gain and phase response blocks 1607a-d, HPAs 1609 a-d, and output hybrid matrix 1611 can then be part ofthe RF payload equipment external to the digital channelizer processorblock 240. In FIG. 2A, this can be thought of as moving in the inputhybrid matrix from the output block 220 to the digital channelizer block240, as is illustrated in FIG. 17.

FIG. 17 is a block diagram of a satellite or other beamforming apparatusfor an example of two input ports and two output ports and repeats manyof the elements of FIG. 2A, but also incorporates a multiport amplifierwith virtual input hybrid matrix and gain and phase equalizers as inFIG. 16. More specifically, the digital channelizer processor block 1640now includes virtual input hybrid matrix and gain and phase equalizersVIHQ w/eq. 1629, as on the left-hand side of FIG. 16 (in a 2×2embodiment), which is no longer in the output block 1620. The otherelements of FIG. 16 can be much as described above with respect to FIG.2A.

By implementing the input hybrid matrix and the gain and phase equalizerblocks 1-4 1603 a-d in a digital embodiment as part of a virtual inputhybrid matrix, this allows for the equalization of the different pathsto performed by use of mathematical algorithms. This allows for lighterweight and higher accuracy relative to an analog embodiment, with thevirtual input hybrid matrix including equalization 1729 beingimplemented as part of the digital portion of the satellite.

Returning to FIG. 16, the block diagram of FIG. 16 also includeselements of an embodiment for some of the elements for determination ofthe parameter values for the gain and phase equalizer blocks 1603 a-dfor the different paths. Similar to the procedure described above forbeamforming system, a spread spectrum signal is injected to the MPA,propagated through the different paths to one of the output ports,extracted and then the extracted is compared to the injected signal bythe MPA calibration block 1690.

The MPA calibration block 1690 is connected to inject the calibrationsignal at the injection ports 1652 a-d into each of the paths of theMPA. The calibration signal can again be a spread spectrum signalgenerated by the MPA calibration block 1690 that has a power level belowthe thermal noise floor of a customer or user signal active in thechannel, allowing the calibration to be performed without disruption inservice of the MPA. The calibration signals are then propagated throughthe gain & phase equalizer blocks 1603 a-d, the gain & phase responseblocks 1605 q-d, high power amplifiers 1609 a-d, and then through outputhybrid matrix 1622, where the propagated calibration signals can beextracted at the calibration extraction ports 1654 a-d. In theembodiment of FIG. 16, the calibration signals are injected after thevirtual input hybrid matrix 1601, but before the gain & phase equalizerblocks 1603 a-d, although other embodiments can be used. For example, inother embodiments the calibration signals could be injected before thevirtual input hybrid matrix 1601. Similarly, the propagated calibrationsignals can be extracted at differing locations to, for example, look aterror from a segment of the MPA's signal path.

Once the MPA calibration block 1690 block receives back the propagatedcalibration signal, this can be compared to the injected signal. Basedon the comparison, the adjustment parameters for the gain & phaseequalizer blocks 1603 a-d can be determined. For example, in a satelliteembodiment, the comparison data can be transmitted to the ground, wherethe adjustment parameters can be computed and transmitted back to thesatellite. In some embodiments, this can be done by a dedicated downlinkto transmit the comparison data to, for example, Network Control Centerat shown at 130 of FIG. 1, and a dedicated uplink to send the adjustmentparameters back. This can simplify the MPA calibration circuitryrequired on the satellite, but requires the link to the ground. In otherembodiments, the parameters can be determined by the MPA calibrationblock 1690, such as by use of look up tables or computation algorithms.

FIG. 18 looks at one embodiment for the MPA calibration block of FIG. 16in more detail. Block 1851 receives a local time reference and from thisgenerates the spread spectrum calibration signal, which then has itspower level adjusted at block 1853, providing the spread signal, lowpower calibration signal for injection. After injection and propagatingthrough a path of the multiport amplifier, the propagated calibrationsignal is extracted. For the satellite example, the MPA up converts anIF frequency signal to an RF frequency signal. Consequently, theinjected signal will be in the IF range and the extracted signal in theRF range and will need to be down converted at block 1843. Similarly, ifthe MPA were to down convert the input signal, the propagated would beup converted at this point; and if there were no frequency rangeconversion, then the block 1843 would be omitted. The propagatedcalibration signal is then received at the multiplier 1859, where it iscombined with the original calibration waveform, the result going to thecorrelation/accumulation block 1854. The resultant comparison data canthen be accumulated at block 1845 and then transmitted out by adownlink, the correction value computed, transmitted back by an uplinkto the gain/phase/delay corrections block 1841. In some embodiments thedownlink and uplinks can be dedicated. In still other embodiments, thegain/phase/delay corrections can be computed on-board. For any of theembodiments, the gain/phase/delay corrections block 1841 can then supplythe adjustment parameters to the gain & phase equalizer blocks 1603 a-d.A scheduler 1857 can determine which paths of the MPA are to becalibrated and when.

FIG. 19 is a flow chart illustrating one embodiment for an MPAcalibration operation using a spread spectrum, low power calibrationsignal as described with respect to FIGS. 14-18 As with the satellitecalibration process described earlier, the use of the spread spectrum,low power calibration signal allows for the MPA to be calibrated whileactive, although the calibration operation can also be performed whenthe multiport amplifier is otherwise not active, such as part of a testmode.

FIG. 19 describes an MPA calibration operation that can be performedwhile the amplifier is active. Beginning at step 1911 a referencesignal, such as a pseudo-random noise signal, is generated by block1851. At step 1913 the spread spectrum calibration signal is thengenerated from the pseudo-random noise sequence and in one embodimentcan reside in a 1 MHz sub channel and set to a power level below thethermal noise floor (such as 17 dB below) of the user signals in the MPApaths. If the calibration signal need to be up-converted ordown-converted, this can be done prior to injecting the calibrationsignal into one or more of the MPA paths at step 1915. The calibrationfor different paths can be performed sequentially according to aschedule based on how quickly the calibration of the different channelsare found to drift. The injected calibration signal is then propagatedthrough selected paths of the MPA at step 1917.

After the injected signal propagates the selected path, it is receivedback at the calibration block at step 1919. If the MPA up-converts thesignals along it path, as FIG. 2C, the extracted calibration signal canthen be down-converted at step 1921. Similarly, if the MPA down-convertssignals, any up-conversion or other needs processes can be done at thistime. The propagated calibration is then de-spread at step 1923. Thede-spread signal can then be compared to the original reference signalat step 1925. In an embodiment where the calibration block does notdetermine the calibration parameters itself, the comparison data is thensent out and the calibration parameters are then received back. Forexample, on a satellite embodiment, the comparison data can then betransmitted out over a dedicated downlink at step 1927 with the computedcalibration updates then received over a dedicated uplink at step 1929.In other embodiments, the updates can be determined as part of thecalibration block 1690. The update corrections are then applied to thegain & phase equalizer blocks 1603 a-d at step 1931.

As with the calibration of a beamforming device, a number of alternateembodiments are possible for the calibration of an MPA. For example, aswith a beamforming system, in an MPA it is the relative path-to-pathphase, gain and delay differences when the signals from the differentpaths are recombined in the output hybrid matrix that usually mattermore than the absolute values. Consequently, the paths can be calibratedbased on path-to-path differences as described above with respect toFIG. 13, rather than with respect to fixed nominal values.

As described with respect to FIG. 10 for the beamforming example, in theMPA calibration process the dwell or integration time for a given pathcan be based on the power in the channel. As a path with a signal oflower power will have a lower S/N value, the dwell or accumulation timefor measurement for determining the error in a path can be made afunction of the power, with less integration time spent on lower powerpaths and only the most powerful signals requiring the maximum dwelltime.

FIG. 15 illustrates the paths from a single input port of an MPA to asingle output port. Rather than running the calibration signal along asingle path at a time, or even from a single input port or to a singleoutput port at a time, the calibration signal can be entered into, andextracted from, multiple ports at the same time. The calibration signalscan be injected into multiple paths/ports, extracted from multiplepaths/ports concurrently, or both and then separated out to determinethe parameters for each of the gain and phase equalizer blocks. Forexample, in each of the four input ports of the virtual hybrid inputmatrix 1401 of FIG. 14 could have a spread spectrum calibration signalinjected at the same time, but with these signals having a relativephase of 90° between each of the ports, allowing these to dedistinguished at the outputs of the output hybrid matrix 1411. This canbe affected either by injection and extraction ports or through use ofprobes such as 1191 of FIG. 11 and 1293 of FIG. 12.

Again, similarly to as described for the beam forming circuitry withrespect to FIG. 9, rather than calibrate the paths of an MPA as a whole,portions of the paths can be calibrated followed by full pathcalibrations.

In a first set of embodiments, an amplifier system includes an inputnetwork having a plurality of input ports and an output network having aplurality of output ports. A plurality of amplification units arecoupled between the input network and the output network, where theplurality of amplification units configured to amplify signals from theplurality of input ports. A plurality of equalizers are each coupledbetween the input network and the output network in series with acorresponding one of the amplification units, and are configured toequalize signal path of the corresponding amplification unit between theinput ports and the output ports. One or more calibration circuits areconfigured to generate a calibration signal and inject the calibrationsignal into a plurality of the paths between the input ports and theoutput ports before the equalizers concurrently with the amplifiersystem propagating one or more user signals along the paths between theinput ports and the output ports. The calibration signal is a spreadspectrum signal with a power level lower than a noise floor of the oneor more user signals. The one or more calibration circuits are furtherconfigured to receive the injected calibration signal from one or moreof the output ports after propagation through the amplifier system andperform a comparison of the injected calibration signal to thecalibration signal after propagating through the amplifier system.

In another set of embodiments, a satellite has multiple receive antennaeand multiple transmit antennae. A multiport amplifier is coupled betweenthe receive antennae and the transmit antennae. The multiport amplifierincludes an input hybrid matrix coupled to multiple ones of the receiveantennae, an output hybrid matrix coupled to multiple ones of thetransmit antennae, and a plurality of amplification units coupledbetween the input hybrid matrix and the output hybrid matrix, theplurality of amplification units configured to amplify signals from theinput hybrid matrix. The multiport amplifier also includes a pluralityof equalizers, each coupled between the virtual input network and theoutput hybrid matrix in series with a corresponding one of theamplification units, the equalizers configured to equalize signal pathsbetween the receive antennae and the transmit antennae through theplurality of amplification units. One or more calibration circuits areconnected to the multiport amplifier, where the calibration circuitsconfigured to generate and inject a calibration signal into a pluralityof signal paths of the multiport amplifier before the equalizersconcurrently with the multiport amplifier propagating one or more usersignals along the signal paths. The calibration signal is a spreadspectrum signal with a power level lower than a noise floor of the oneor more user signals. The one or more calibration circuits are furtherconfigured to receive the injected calibration signal after propagationthrough the multiport amplifier and perform a comparison of the injectedcalibration signal to the calibration signal after propagating throughthe multiport amplifier.

Other embodiments present methods including performing a calibrationoperation on a multiport amplifier circuit. The calibration operationincludes generating a spread spectrum calibration signal; injecting thespread spectrum calibration signal into one or more paths of a multiportamplifier; and receiving the injected calibration signal afterpropagating through at least a portion of the one or more paths of themultiport amplifier. A comparison is performed of the injectedcalibration signal to the calibration signal after propagating throughthe portion of the one or more paths of the multiport amplifier. Acalibration operation is performed on the multiport amplifier withparameters based on the comparison.

For purposes of this document, it should be noted that the dimensions ofthe various features depicted in the figures may not necessarily bedrawn to scale.

For purposes of this document, reference in the specification to “anembodiment,” “one embodiment,” “some embodiments,” or “anotherembodiment” may be used to describe different embodiments or the sameembodiment.

For purposes of this document, a connection may be a direct connectionor an indirect connection (e.g., via one or more other parts). In somecases, when an element is referred to as being connected or coupled toanother element, the element may be directly connected to the otherelement or indirectly connected to the other element via interveningelements. When an element is referred to as being directly connected toanother element, then there are no intervening elements between theelement and the other element. Two devices are “in communication” ifthey are directly or indirectly connected so that they can communicateelectronic signals between them.

For purposes of this document, the term “based on” may be read as “basedat least in part on.”

For purposes of this document, without additional context, use ofnumerical terms such as a “first” object, a “second” object, and a“third” object may not imply an ordering of objects, but may instead beused for identification purposes to identify different objects.

For purposes of this document, the term “set” of objects may refer to a“set” of one or more of the objects.

The foregoing detailed description has been presented for purposes ofillustration and description. It is not intended to be exhaustive or tolimit to the precise form disclosed. Many modifications and variationsare possible in light of the above teaching. The described embodimentswere chosen in order to best explain the principles of the proposedtechnology and its practical application, to thereby enable othersskilled in the art to best utilize it in various embodiments and withvarious modifications as are suited to the particular use contemplated.It is intended that the scope be defined by the claims appended hereto.

What is claimed is:
 1. An amplifier system, comprising: an input network having a plurality of input ports; an output network having a plurality of output ports; a plurality of amplification units coupled between the input network and the output network, the plurality of amplification units configured to amplify signals from the plurality of input ports; a plurality of equalizers, each coupled between the input network and the output network in series with a corresponding one of the amplification units and configured to equalize signal path of the corresponding amplification unit between the input ports and the output ports; and one or more calibration circuits configured to generate a calibration signal and inject the calibration signal into a plurality of the paths between the input ports and the output ports before the equalizers concurrently with the amplifier system propagating one or more user signals along the paths between the input ports and the output ports, the calibration signal being a spread spectrum signal with a power level lower than a noise floor of the one or more user signals, the one or more calibration circuits further configured to receive the injected calibration signal from one or more of the output ports after propagation through the amplifier system and perform a comparison of the injected calibration signal to the calibration signal after propagating through the amplifier system.
 2. The amplifier system of claim 1, wherein the input network and the equalizers are part of a digitally implemented virtual input hybrid matrix.
 3. The amplifier system of claim 1, wherein the one or more calibration circuits are coupled to the equalizers and configured to individually adjust signal paths propagating therethrough.
 4. The amplifier system of claim 3, wherein the one or more calibration circuits are configured to adjust a phase of signals propagating through the equalizers.
 5. The amplifier system of claim 3, wherein the one or more calibration circuits are configured to adjust an amplitude of signals propagating through the equalizers.
 6. The amplifier system of claim 3, wherein the one or more calibration circuits are configured to determine parameters to individually adjust signal paths propagating though the equalizers based on the comparison of the injected calibration signal to the calibration signal after propagating through the amplifier system.
 7. The amplifier system of claim 6, wherein the parameters are determined based on path to path differences between the plurality of paths.
 8. The amplifier system of claim 3, wherein the one or more calibration circuits are configured to provide data based on the comparison of the injected calibration signal to the calibration signal after propagating through the amplifier system and to receive parameters to individually adjust signal paths propagating though the equalizers.
 9. The amplifier system of claim 1, wherein the one or more calibration circuits are configured to inject the calibration signal into the plurality of paths after the input network.
 10. The amplifier system of claim 1, wherein the one or more calibration circuits are configured to inject the calibration signal into the plurality of paths before the input network.
 11. The amplifier system of claim 10, wherein the one or more calibration circuits are configured to inject the calibration signal into a plurality of the input ports concurrently.
 12. The amplifier system of claim 1, wherein the one or more calibration circuits are configured to receive the injected calibration signal from a plurality of the output ports concurrently.
 13. A satellite, comprising: a plurality of receive antennae; a plurality of transmit antennae; a multiport amplifier coupled between the plurality of receive antennae and the plurality of transmit antennae, the multiport amplifier including: an input hybrid matrix coupled to multiple ones of the receive antennae; an output hybrid matrix coupled to multiple ones of the transmit antennae; a plurality of amplification units coupled between the input hybrid matrix and the output hybrid matrix, the plurality of amplification units configured to amplify signals from the input hybrid matrix; and a plurality of equalizers, each coupled between the input hybrid network and the output hybrid matrix in series with a corresponding one of the amplification units, the equalizers configured to equalize signal paths between the receive antennae and the transmit antennae through the plurality of amplification units; and one or more calibration circuits connected to the multiport amplifier, the calibration circuits configured to generate and inject a calibration signal into a plurality of signal paths of the multiport amplifier before the equalizers concurrently with the multiport amplifier propagating one or more user signals along the signal paths, the calibration signal being a spread spectrum signal with a power level lower than a noise floor of the one or more user signals, the one or more calibration circuits further configured to receive the injected calibration signal after propagation through the multiport amplifier and perform a comparison of the injected calibration signal to the calibration signal after propagating through the multiport amplifier.
 14. The satellite of claim 13, wherein the input hybrid matrix and the equalizers are part of a digitally implemented virtual input hybrid matrix.
 15. The satellite of claim 13, wherein the one or more calibration circuits are coupled to the equalizers and configured to individually adjust signal paths propagating therethrough.
 16. The satellite of claim 15, further comprising: a downlink channel whereby the one or more calibration circuits are configured to provide data based on the comparison of the injected calibration signal to the calibration signal after propagating through the multiport amplifier; and an uplink channel whereby the one or more calibration circuits are configured to receive parameters to individually adjust signal paths propagating though the equalizers. 